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a
FEATURES Low Noise: 80 nV p-p (0.1 Hz to 10 Hz), 3 nV//Hz Low Drift: 0.2 V/ C High Speed: 2.8 V/ s Slew Rate, 8 MHz Gain Bandwidth Low VOS: 10 V Excellent CMRR: 126 dB at VCM of 11 V High Open-Loop Gain: 1.8 Million Fits 725, OP07, 5534A Sockets Available in Die Form GENERAL DESCRIPTION
Low-Noise, Precision Operational Amplifier OP27
PIN CONNECTIONS TO-99 (J-Suffix)
BAL BAL 1 -IN 2 +IN 3 V+ OUT NC
OP27
The OP27 precision operational amplifier combines the low offset and drift of the OP07 with both high speed and low noise. Offsets down to 25 mV and maximum drift of 0.6 mV/C, makes the OP27 ideal for precision instrumentation applications. Exceptionally low noise, en = 3.5 nV//Hz, at 10 Hz, a low 1/f noise corner frequency of 2.7 Hz, and high gain (1.8 million), allow accurate high-gain amplification of low-level signals. A gain-bandwidth product of 8 MHz and a 2.8 V/msec slew rate provides excellent dynamic accuracy in high-speed, dataacquisition systems. A low input bias current of 10 nA is achieved by use of a bias-current-cancellation circuit. Over the military temperature range, this circuit typically holds IB and IOS to 20 nA and 15 nA, respectively. The output stage has good load driving capability. A guaranteed swing of 10 V into 600 W and low output distortion make the OP27 an excellent choice for professional audio applications.
(Continued on page 7)
4V- (CASE) NC = NO CONNECT
8-Pin Hermetic DIP (Z-Suffix) Epoxy Mini-DIP (P-Suffix) 8-Pin SO (S-Suffix)
VOS TRIM 1 -IN 2 +IN 3 V- 4
8 7 6 5
OP27
VOS TRIM V+ OUT NC
NC = NO CONNECT
SIMPLIFIED SCHEMATIC
V+ R3 Q6 R1* 1 8 R4 R2* C2 Q22 Q21 R23 Q23 R24 Q24 R9 Q20 Q1A NONINVERTING INPUT (+) Q3 INVERTING INPUT (-) *R1 AND R2 ARE PERMANENTLY ADJUSTED AT WAFER TEST FOR MINIMUM OFFSET VOLTAGE. V- Q11 Q12 Q27 Q28 Q26 Q45 Q1B Q2B Q2A R5 C3 R12 C4 Q19 OUTPUT C1 Q46
VOS ADJ.
REV. C
Information furnished by Analog Devices is believed to be accurate and reliable. However, no responsibility is assumed by Analog Devices for its use, nor for any infringements of patents or other rights of third parties that may result from its use. No license is granted by implication or otherwise under any patent or patent rights of Analog Devices. Trademarks and registered trademarks are the property of their respective companies.
One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A. Tel: 781/329-4700 www.analog.com Fax: 781/326-8703 (c) 2003 Analog Devices, Inc. All rights reserved.
OP27-SPECIFICATIONS
ELECTRICAL CHARACTERISTICS (@ V = 15 V, T = 25 C, unless otherwise noted.)
S A
Parameter INPUT OFFSET VOLTAGE1 LONG-TERM VOS STABILITY2, 3 INPUT OFFSET CURRENT INPUT BIAS CURRENT INPUT NOISE VOLTAGE3, 4 INPUT NOISE Voltage Density3 INPUT NOISE Current Density3, 5 INPUT RESISTANCE Differential-Mode6 Common-Mode INPUT VOLTAGE RANGE
Symbol VOS VOS/Time IOS IB en p-p en
Conditions
Min
OP27A/E Typ Max 10 0.2 7 10 25 1.0 35 40 0.18 5.5 4.5 3.8 4.0 2.3 0.6
Min
OP27F Typ Max 20 0.3 9 12 0.08 3.5 3.1 3.0 1.7 1.0 0.4 60 1.5 50 55 0.18 5.5 4.5 3.8 4.0 2.3 0.6
Min
OP27C/G Typ Max 30 0.4 12 15 0.09 3.8 3.3 3.2 1.7 1.0 0.4 100 2.0 75 80 0.25 8.0 5.6 4.5
Unit mV mV/MO nA nA mV p-p nV//Hz nV//Hz nV//Hz pA//Hz pA//Hz pA//Hz
0.1 Hz to 10 Hz fO = 10 Hz fO = 30 Hz fO = 1000 Hz fO = 10 Hz fO = 30 Hz fO = 1000 Hz
0.08 3.5 3.1 3.0 1.7 1.0 0.4
in
0.6
RIN RINCM IVR VCM = 11 V VS = 4 V to 18 V RL 2 kW, VO = 10 V RL 600 W, VO = 10 V RL 2 kW RL 600 W RL 2 kW
1.3
6 3
0.94
5 2.5
0.7
4 2
MW GW V dB 20 mV/V V/mV V/mV V V V/ms
11.0 12.3 114 126 1 1000 800 1800 1500 10
11.0 12.3 106 123 1 1000 800 1800 1500 10
11.0 12.3 100 120 2 700 600 1500 1500
COMMON-MODE REJECTION RATIO CMRR POWER SUPPLY PSRR REJECTION RATIO LARGE-SIGNAL VOLTAGE GAIN AVO
OUTPUT VOLTAGE SWING SLEW RATE7 GAIN BANDWIDTH PRODUCT7 OPEN-LOOP OUTPUT RESISTANCE POWER CONSUMPTION OFFSET ADJUSTMENT RANGE
VO SR
12.0 13.8 10.0 11.5 1.7 2.8
12.0 13.8 10.0 11.5 1.7 2.8
11.5 13.5 10.0 11.5 1.7 2.8
GBW
5.0
8.0
5.0
8.0
5.0
8.0
MHz
RO Pd
VO = 0, IO = 0 VO
70 90 140
70 90 140
70 100 170
W mW
RP = 10 kW
4.0
4.0
4.0
mV
NOTES 1 Input offset voltage measurements are performed ~ 0.5 seconds after application of power. A/E grades guaranteed fully warmed up. 2 Long-term input offset voltage stability refers to the average trend line of V OS versus. Time over extended periods after the first 30 days of operation. Excluding the initial hour of operation, changes in V OS during the first 30 days are typically 2.5 mV. Refer to typical performance curve. 3 Sample tested. 4 See test circuit and frequency response curve for 0.1 Hz to 10 Hz tester. 5 See test circuit for current noise measurement. 6 Guaranteed by input bias current. 7 Guaranteed by design.
-2-
REV. C
OP27 ELECTRICAL CHARACTERISTICS
Parameter INPUT OFFSET VOLTAGE1 AVERAGE INPUT OFFSET DRIFT INPUT OFFSET CURRENT INPUT BIAS CURRENT INPUT VOLTAGE RANGE Symbol VOS TCVOS2 TCVOSn3 IOS IB IVR VCM = 10 V VS = 4.5 V to 18 V RL 2 kW, VO = 10 V 600 RL 2 kW 11.5 10.3 108
(@ VS = 15 V, -55 C TA 125 C, unless otherwise noted.)
Min OP27A Typ 30 Max 60 Min OP27C Typ 70 Max 300 Unit mV
Conditions
0.2 15 20 11.5 122 2 1200 13.5
0.6 50 60 10.2 94 16 300 10.5
4 30 35 11.5 118 4 800 13.0
1.8 135 150
mV/C nA nA V dB
COMMON-MODE REJECTION RATIO CMRR POWER SUPPLY REJECTION RATIO PSRR LARGE-SIGNAL VOLTAGE GAIN OUTPUT VOLTAGE SWING AVO VO
51
mV/V V/mV V
NOTES 1 Input offset voltage measurements are performed by automated test equipment approximately 0.5 seconds after application of power. A/E grades guaranteed fully warmed up. 2 The TCVOS performance is within the specifications unnulled or when nulled with R P = 8 kW to 20 kW. TCVOS is 100% tested for A/E grades, sample tested for C/F/G grades. 3 Guaranteed by design.
REV. C
-3-
OP27
ELECTRICAL CHARACTERISTICS
Parameter INPUT ONSET VOLTAGE AVERAGE INPUT OFFSET DRIFT INPUT OFFSET CURRENT INPUT BIAS CURRENT INPUT VOLTAGE RANGE Symbol VOS TCVOS1 TCVOSn2 IOS IB IVR VCM = 10 V VS = 4.5 V to 18 V RL 2 kW, VO = 10 V RL 2 kW 10.5 110 Conditions
(@ VS = 15 V, -25 C TA 85 C for OP27J, OP27Z, 0 C TA 70 C for OP27EP, OP27FP, and -40 C TA 85 C for OP27GP, OP27GS, unless otherwise noted.)
Min OP27E Typ 20 0.2 0.2 10 14 11.8 124 2 15 Max 50 0.6 0.6 50 60 Min OP27F Typ Max 40 0.3 0.3 14 18 10.5 11.8 102 121 2 16 140 1.3 1.3 85 95 Min OP27G Typ Max 55 04 04 20 25 10.5 11.8 96 118 2 32 220 1.8 1.8 135 150 Unit mV mV/C mV/C nA nA V dB mV/V
COMMON-MODE REJECTION RATIO CMRR POWER SUPPLY REJECTION RATIO PSRR LARGE-SIGNAL VOLTAGE GAIN OUTPUT VOLTAGE SWING
AVO
750 11.7
1500 13.6
700
1300
450
1000
V/mV V
VO
11.4 13.5
11.0 13.3
NOTES 1 The TCVOS performance is within the specifications unnulled or when nulled with R P = 8 kW to 20 kW. TCVOS is 100% tested for A/E grades, sample tested for C/F/G grades. 2 Guaranteed by design.
-4-
REV. C
OP27
DIE CHARACTERISTICS
1. 2. 3. 4. 6. 7. 8. NULL (-) INPUT (+) INPUT V- OUTPUT V+ NULL
1
1990
1427U
8
2
3
7 4 6
WAFER TEST LIMITS
Parameter
(@ VS = 15 V, TA = 25 C unless otherwise noted.)
Symbol VOS IOS IB IVR CMRR PSRR AVO AVO VO VO Pd VCM = IVR VS = 4 V to 18 V RL 2 kW, VO = 10 V RL 600 W, VO = 10 V RL 2 kW RL2600n VO = 0 Conditions OP27N Limit 35 35 40 11 114 10 1000 800 12.0 10.0 140 OP27G Limit 60 50 55 11 106 10 1000 800 12.0 10.0 140 OP27GR Limit 100 75 80 11 100 20 700 600 +11.5 10.0 170 Unit mV Max nA Max nA Max V Min dB Min mV/V Max V/mV Min V/mV Min V Min V Min mW Max
INPUT OFFSET VOLTAGE* INPUT OFFSET CURRENT INPUT BIAS CURRENT INPUT VOLTAGE RANGE COMMON-MODE REJECTION RATIO POWER SUPPLY LARGE-SIGNAL VOLTAGE GAIN OUTPUT VOLTAGE SWING POWER CONSUMPTION
NOTE *Electrical tests are performed at wafer probe to the limits shown. Due to variations in assembly methods and normal yield loss, yield after packaging is not guaranteed for standard product dice. Consult factory to negotiate specifications based on dice lot qualification through sample lot assembly and testing.
REV. C
-5-
OP27
TYPICAL ELECTRICAL CHARACTERISTICS (@ V = 15 V, T = 25 C unless otherwise noted.)
S A
Parameter AVERAGE INPUT OFFSET VOLTAGE DRIFT* AVERAGE INPUT OFFSET CURRENT DRIFT AVERAGE INPUT BIAS CURRENT DRIFT INPUT NOISE VOLTAGE DENSITY
Symbol TCVOS or TCVOSn TCIOS TCIB en en en in in in enp-p SR GBW
Conditions Nulled or Unnulled RP = 8 kW to 20 kW
OP27N Typical 0.2
OP27G Typical 0.3
OP27GR Typical 0.4
Unit mV/C
80 100 fO = 10 Hz fO = 30 Hz fO = 1000 Hz fO = 10 Hz fO = 30 Hz fO = 1000 Hz 0.1 Hz to 10 Hz RL 2 kW 3.5 3.1 3.0 1.7 1.0 0.4 0.08 2.8 8
130 160 3.5 3.1 3.0 1.7 1.0 0.4 0.08 2.8 8
180 200 3.8 3.3 3.2 1.7 1.0 0.4 0.09 2.8 8
pA/C pA/C nV//Hz nV//Hz nV//Hz pA//Hz pA//Hz pA//Hz mV p-p V/ms MHz
INPUT NOISE CURRENT DENSITY
INPUT NOISE VOLTAGE SLEW RATE GAIN BANDWIDTH PRODUCT
NOTE *Input offset voltage measurements are performed by automated test equipment approximately 0.5 seconds after application of power.
-6-
REV. C
OP27
(Continued from page 1)
PSRR and CMRR exceed 120 dB. These characteristics, coupled with long-term drift of 0.2 mV/month, allow the circuit designer to achieve performance levels previously attained only by discrete designs. Low-cost, high-volume production of OP27 is achieved by using an on-chip Zener zap-trimming network. This reliable and stable offset trimming scheme has proved its effectiveness over many years of production history.
The OP27 provides excellent performance in low-noise, highaccuracy amplification of low-level signals. Applications include stable integrators, precision summing amplifiers, precision voltagethreshold detectors, comparators, and professional audio circuits such as tape-head and microphone preamplifiers. The OP27 is a direct replacement for 725, OP06, OP07, and OP45 amplifiers; 741 types may be directly replaced by removing the 741's nulling potentiometer.
ABSOLUTE MAXIMUM RATINGS 4
Supply Voltage . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 22 V Input Voltage1 . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 22 V Output Short-Circuit Duration . . . . . . . . . . . . . . . . Indefinite Differential Input Voltage2 . . . . . . . . . . . . . . . . . . . . . . 0.7 V Differential Input Current2 . . . . . . . . . . . . . . . . . . . . 25 mA Storage Temperature Range . . . . . . . . . . . . -65C to +150C Operating Temperature Range OP27A, OP27C (J, Z) . . . . . . . . . . . . . . . . -55C to +125C OP27E, OP27F (J, Z) . . . . . . . . . . . . . . . . . -25C to +85C OP27E, OP27F (P) . . . . . . . . . . . . . . . . . . . . . . 0C to 70C OP27G (P, S, J, Z) . . . . . . . . . . . . . . . . . . -40C to +85C Lead Temperature Range (Soldering, 60 sec) . . . . . . . 300C Junction Temperature . . . . . . . . . . . . . . . . . -65C to +150C
Package Type TO 99 (J) 8-Lead Hermetic DlP (Z) 8-Lead Plastic DIP (P) 20-Contact LCC (RC) 8-Lead SO (S)
3 JA
JC
Unit C/W C/W C/W C/W C/W
150 148 103 98 158
18 16 43 38 43
NOTES 1 For supply voltages less than 22 V, the absolute maximum input voltage is equal to the supply voltage. 2 The OP27's inputs are protected by back-to-back diodes. Current limiting resistors are not used in order to achieve low noise. If differential input voltage exceeds 0.7 V, the input current should be limited to 25 mA. 3 JA is specified for worst-case mounting conditions, i.e., JA is specified for device in socket for TO, CERDIP, and P-DIP packages; JA is specified for device soldered to printed circuit board for SO package. 4 Absolute Maximum Ratings apply to both DICE and packaged parts, unless otherwise noted.
ORDERING INFORMATION 1
Package TA = 25C VOS Max (mV) 25 25 60 100 100 100 CERDIP 8-Lead OP27AZ2 OP27EZ OP27CZ3 OP27GZ Plastic 8-Lead OP27EP OP27FP3 OP27GP OP27GS4 Operating Temperature Range MIL IND/COM IND/COM MIL XIND XIND
TO-99 OP27AJ2, 3 OP27EJ2, 3
OP27GJ
NOTES 1 Burn-in is available on commercial and industrial temperature range parts in CERDIP, plastic DIP, and TO-can packages. 2 For devices processed in total compliance to MIL-STD-883, add /883 after part number. Consult factory for 883 data sheet. 3 Not for new design; obsolete April 2002. 4 For availability and burn-in information on SO and PLCC packages, contact your local sales office.
CAUTION ESD (electrostatic discharge) sensitive device. Electrostatic charges as high as 4000 V readily accumulate on the human body and test equipment and can discharge without detection. Although the OP27 features proprietary ESD protection circuitry, permanent damage may occur on devices subjected to high-energy electrostatic discharges. Therefore, proper ESD precautions are recommended to avoid performance degradation or loss of functionality.
WARNING!
ESD SENSITIVE DEVICE
REV. C
-7-
OP27-Typical Performance Characteristics
100 90
VOLTAGE NOISE - nV/ Hz
80
GAIN - dB
5 4 3 I/F CORNER = 2.7Hz
70 60 50 40 30 0.01 TEST TIME OF 10sec FURTHER LIMITS LOW FREQUENCY (<0.1Hz) GAIN
VOLTAGE NOISE - nV/ Hz
10 9 8 7 6
100
TA = 25 C VS = 15V
741
2
I/F CORNER 10 I/F CORNER = LOW NOISE 2.7Hz AUDIO OP AMP OP27 I/F CORNER INSTRUMENTATION AUDIO RANGE RANGE TO DC TO 20kHz
1
1
1 10 100 FREQUENCY - Hz 1k
0.1
1 10 FREQUENCY - Hz
100
1
10 100 FREQUENCY - Hz
1k
TPC 1. 0.1 Hz to 10 Hzp-p Noise Tester Frequency Response
TPC 2. Voltage Noise Density vs. Frequency
TPC 3. A Comparison of Op Amp Voltage Noise Spectra
10 TA = 25 C VS = 15V
100 TA = 25 C VS = 15V R1 R2 RS - 2R1
5 VS = 15V
V
VOLTAGE NOISE - nV/ Hz
TOTAL NOISE - nV/ Hz
RMS VOLTAGE NOISE -
4 AT 10Hz
1
10
3 AT 1kHz
0.1
AT 10Hz AT 1kHz RESISTOR NOISE ONLY
2
0.01 100
1k 10k BANDWIDTH - Hz
100k
1 100
1k SOURCE RESISTANCE -
10k
1 -50
-25
0 25 50 75 TEMPERATURE - C
100
125
TPC 4. Input Wideband Voltage Noise vs. Bandwidth (0.1 Hz to Frequency Indicated)
TPC 5. Total Noise vs. Sourced Resistance
TPC 6. Voltage Noise Density vs. Temperature
5
TA = 25 C
10.0
5.0
CURRENT NOISE - pA/ Hz
VOLTAGE NOISE - nV/ Hz
4 AT 10Hz AT 1kHz 3
SUPPLY CURRENT - mA
4.0 TA = +125 C 3.0 TA = -55 C 2.0 TA = +25 C
1.0
2
I/F CORNER = 140Hz 1 0.1 10
0
10
20
30
40
TOTAL SUPPLY VOLTAGE (V+ - V-) - V
100 1k FREQUENCY - Hz
10k
1.0
5
15 25 35 TOTAL SUPPLY VOLTAGE - V
45
TPC 7. Voltage Noise Density vs. Supply Voltage
TPC 8. Current Noise Density vs. Frequency
TPC 9. Supply Current vs. Supply Voltage
-8-
REV. C
OP27
CHANGE IN INPUT OFFSET VOLTAGE - V
60 50 40
OFFSET VOLTAGE - V
OP27C
CHANGE IN OFFSET VOLTAGE - V
6 4 2 0 -2 -4 -6 6 4 2 0 -2 -4 -6 0 1 2 3 4 5 6 7 TIME - Months
TA = 25 C VS = 15V
30 20 10 0 -10 -20 -30 -40 -50 -60 TRIMMING WITH 10k POT DOES NOT CHANGE TCVOS
OP27A
10
OP27 C/G
OP27 F
OP27A OP27A
5
OP27 A/E
-70 -75 -50 -25
OP27C
0 25 50 75 100 125 150 175 TEMPERATURE - C
1
0
1
2
3
4
5
TIME AFTER POWER ON - Min
TPC 10. Offset Voltage Drift of Five Representative Units vs. Temperature
TPC 11. Long-Term Offset Voltage Drift of Six Representative Units
TPC 12. Warm-Up Offset Voltage Drift
30 VS = 25 15V
INPUT BIAS CURRENT - nA
50 VS = 40 15V
INPUT OFFSET CURRENT - nA
50 VS = 40 15V
OPEN-LOOP GAIN - dB
20
TA = 25 C
TA = 70 C
30
30
15
THERMAL SHOCK RESPONSE BAND
20 OP27C 10 OP27A 0
20 OP27C 10 OP27A
10 5 0 -20
DEVICE IMMERSED IN 70 C OIL BATH
0
20
40 TIME - Sec
60
80
100
-50 -25
0
25
50
75
100 125 150
0 -75 -50
TEMPERATURE - C
-25 0 25 50 75 TEMPERATURE - C
100
125
TPC 13. Offset Voltage Change Due to Thermal Shock
TPC 14. Input Bias Current vs. Temperature
TPC 15. Input Offset Current vs. Temperature
130 110
VOLTAGE GAIN - dB
PHASE MARGIN - Degrees
25
10
80 TA = 25 C VS = 15V GAIN 100 120 PHASE MARGIN = 70 140 160 180 200 220 100M
70
M
GAIN BANDWIDTH PRODUCT - MHz
20 15
90 70 50 30 10 -10
VS =
15V
9
60
10 5 0 -5
50
GBW
8
SLEW RATE - V/ s
4
3
SLEW
7
2
-75
1
10
100
1k 10k 100k 1M 10M 100M FREQUENCY - Hz
-50 -25
0
25
50
75
6 100 125
-10 1M
TEMPERATURE - C
10M FREQUENCY - Hz
TPC 16. Open-Loop Gain vs. Frequency
TPC 17. Slew Rate, Gain-Bandwidth Product, Phase Margin vs. Temperature
TPC 18. Gain, Phase Shift vs. Frequency
REV. C
-9-
PHASE SHIFT - Degrees
GAIN - dB
OP27
2.5 TA = 25 C
PEAK-TO-PEAK AMPLITUDE - V
28 24 20 16 12 8 4 0 1k
TA = 25 C VS = 15V MAXIMUM OUTPUT - V
18 16 14 12 10 8 6 4 2 0 TA = 25 C VS = 15V 1k LOAD RESISTANCE - 10k NEGATIVE SWING POSITIVE SWING
OPEN-LOOP GAIN - V/ V
2.0 RL = 2k 1.5 RL = 1k 1.0
0.5
0
0
10
20
30
40
50
10k
TOTAL SUPPLY VOLTAGE - V
100k 1M FREQUENCY - Hz
10M
-2 100
TPC 19. Open-Loop Voltage Gain vs. Supply Voltage
TPC 20. Maximum Output Swing vs. Frequency
TPC 21. Maximum Output Voltage vs. Load Resistance
100 VS = 15V VIN = 100mV AV = +1
50mV
80
20mV
500ns AVCL = +1 CL = 15pF VS = 15V TA = 25 C
2V +5V
2s AVCL = +1 VS = 15V TA = 25 C
% OVERSHOOT
60
0V
0V
40
-50mV
-5V
20
0
0
500
1000
1500
2000
2500
CAPACITIVE LOAD - pF
TPC 22. Small-Signal Overshoot vs. Capacitive Load
TPC 23. Small-Signal Transient Response
TPC 24. Large-Signal Transient Response
60
140
16
VS = 15V TA = 25 C VCM = 10V
SHORT-CIRCUIT CURRENT - mA
TA = 25 C VS = 15V 50
120
12
TA = -55 C TA = +25 C
COMMON-MODE RANGE - V
8 TA = +125 C 4 0 TA = -55 C -4 TA = +25 C -8 -12 TA = +125 C
40
ISC(+)
CMRR - dB
100
30
ISC(-)
80
20
10
0
1
2
3
4
5
60 100
1k
TIME FROM OUTPUT SHORTED TO GROUND - Min
10k 100k FREQUENCY - Hz
1M
-16
0
5
10
15
20
SUPPLY VOLTAGE - V
TPC 25. Short-Circuit Current vs. Time
TPC 26. CMRR vs. Frequency
TPC 27. Common-Mode Input Range vs. Supply Voltage
-10-
REV. C
OP27
0.1 F 100k
OPEN-LOOP VOLTAGE GAIN - V/ V
2.4 2.2 2.0 1.8 1.6 1.4 1.2 1.0 0.8 0.6 0.4 100
0.1Hz to 10Hz p-p NOISE VOLTAGE NOISE - nV
TA = 25 C VS = 15V
1 SEC/DIV 120 80 40 0 -40 -90 -120
10
OP27 D.U.T.
VOLTAGE GAIN = 50,000 4.7 F
2k 4.3k OP12 100k 0.1 F 2.2 F 24.3k SCOPE 1 RIN = 1M 110k 22 F
1k 10k LOAD RESISTANCE -
100k
TPC 28. Voltage Noise Test Circuit (0.1 Hz to 10 Hz)
TPC 29. Open-Loop Voltage Gain vs. Load Resistance
TPC 30. Low-Frequency Noise
160
POWER SUPPLY REJECTION RATIO - dB
140 120 100 80 60 40 20 0 POSITIVE SWING NEGATIVE SWING
TA = 25 C
1
10
100
1k 10k 100k 1M 10M 100M FREQUENCY - Hz
TPC 31. PSRR vs. Frequency
APPLICATION INFORMATION OFFSET VOLTAGE ADJUSTMENT
OP27 series units may be inserted directly into 725 and OP07 sockets with or without removal of external compensation or nulling components. Additionally, the OP27 may be fitted to unnulled 741-type sockets; however, if conventional 741 nulling circuitry is in use, it should be modified or removed to ensure correct OP27 operation. OP27 offset voltage may be nulled to zero (or another desired setting) using a potentiometer (see Figure 1). The OP27 provides stable operation with load capacitances of up to 2000 pF and 10 V swings; larger capacitances should be decoupled with a 50 W resistor inside the feedback loop. The OP27 is unity-gain stable. Thermoelectric voltages generated by dissimilar metals at the input terminal contacts can degrade the drift performance. Best operation will be obtained when both input contacts are maintained at the same temperature.
10k RP V+
The input offset voltage of the OP27 is trimmed at wafer level. However, if further adjustment of VOS is necessary, a 10 kW trim potentiometer can be used. TCVOS is not degraded (see Offset Nulling Circuit). Other potentiometer values from 1 kW to 1 MW can be used with a slight degradation (0.1 mV/C to 0.2 mV/C) of TCVOS. Trimming to a value other than zero creates a drift of approximately (VOS/300) mV/C. For example, the change in TCVOS will be 0.33 mV/C if VOS is adjusted to 100 mV. The offset voltage adjustment range with a 10 kW potentiometer is 4 mV. If smaller adjustment range is required, the nulling sensitivity can be reduced by using a smaller pot in conjuction with fixed resistors. For example, Figure 2 shows a network that will have a 280 mV adjustment range.
1 4.7k 1k POT 4.7k 8
V+
Figure 2. Offset Voltage Adjustment
-
OP27
+
OUTPUT
V-
Figure 1. Offset Nulling Circuit
REV. C
-11-
OP27
NOISE MEASUREMENTS
To measure the 80 nV peak-to-peak noise specification of the OP27 in the 0.1 Hz to 10 Hz range, the following precautions must be observed: 1. The device must be warmed up for at least five minutes. As shown in the warm-up drift curve, the offset voltage typically changes 4 mV due to increasing chip temperature after power-up. In the 10-second measurement interval, these temperature-induced effects can exceed tens-ofnanovolts. 2. For similar reasons, the device has to be well-shielded from air currents. Shielding minimizes thermocouple effects. 3. Sudden motion in the vicinity of the device can also "feedthrough" to increase the observed noise. 4. The test time to measure 0.1 Hz to 10 Hz noise should not exceed 10 seconds. As shown in the noise-tester frequency response curve, the 0.1 Hz corner is defined by only one zero. The test time of 10 seconds acts as an additional zero to eliminate noise contributions from the frequency band below 0.1 Hz. 5. A noise-voltage-density test is recommended when measuring noise on a large number of units. A 10 Hz noise-voltagedensity measurement will correlate well with a 0.1 Hz to 10 Hz peak-to-peak noise reading, since both results are determined by the white noise and the location of the 1/f corner frequency. When R f 100 W and the input is driven with a fast, large signal pulse (>1 V), the output waveform will look as shown in the pulsed operation diagram (Figure 3). During the fast feedthrough-like portion of the output, the input protection diodes effectively short the output to the input and a current, limited only by the output short-circuit protection, will be drawn by the signal generator. With Rf 500 W, the output is capable of handling the current requirements (IL 20 mA at 10 V); the amplifier will stay in its active mode and a smooth transition will occur. When Rf > 2 kW, a pole will be created with Rf and the amplifier's input capacitance (8 pF) that creates additional phase shift and reduces phase margin. A small capacitor (20 pF to 50 pF) in parallel with R f will eliminate this problem.
Rf
bias and offset currents, which would normally increase, are held to reasonable values by the input bias-current cancellation circuit. The OP27A/E has IB and IOS of only 40 nA and 35 nA at 25C respectively. This is particularly important when the input has a high source resistance. In addition, many audio amplifier designers prefer to use direct coupling. The high IB, VOS, and TCVOS of previous designs have made direct coupling difficult, if not impossible, to use. Voltage noise is inversely proportional to the square root of bias current, but current noise is proportional to the square root of bias current. The OP27's noise advantage disappears when high source-resistors are used. Figures 4, 5, and 6 compare OP27's observed total noise with the noise performance of other devices in different circuit applications.
E(Voltage Noise)2 + I 2 I Total Noise = I(Current Noise RS ) + I 2 I(Resistor Noise ) I
1/2
Figure 4 shows noise versus source-resistance at 1000 Hz. The same plot applies to wideband noise. To use this plot, multiply the vertical scale by the square root of the bandwidth.
100
50
UNITY-GAIN BUFFER APPLICATIONS
1
TOTAL NOISE - nV/ Hz
OP08/108 2 OP07 10
1 RS e.g. RS 2 RS e.g. RS UNMATCHED = R S1 = 10k , R S2 = 0 MATCHED = 10k , R S1 = R S2 = 5k RS1
5
5534 OP27/37 REGISTER NOISE ONLY 100
RS2
1 50
10k 500 1k 5k RS - SOURCE RESISTANCE -
50k
Figure 4. Noise vs. Source Resistance (Including Resistor Noise) at 1000 Hz
-
OP27
+
2.8V/ s
At RS <1 kW, the OP27's low voltage noise is maintained. With RS <1 kW, total noise increases, but is dominated by the resistor noise rather than current or voltage noise. lt is only beyond RS of 20 kW that current noise starts to dominate. The argument can be made that current noise is not important for applications with low to moderate source resistances. The crossover between the OP27, OP07, and OP08 noise occurs in the 15 kW to 40 kW region. Figure 5 shows the 0.1 Hz to 10 Hz peak-to-peak noise. Here the picture is less favorable; resistor noise is negligible and current noise becomes important because it is inversely proportional to the square root of frequency. The crossover with the OP07 occurs in the 3 kW to 5 kW range depending on whether balanced or unbalanced source resistors are used (at 3 kW the IB and IOS error also can be three times the VOS spec.).
Figure 3. Pulsed Operation
COMMENTS ON NOISE
The OP27 is a very low-noise monolithic op amp. The outstanding input voltage noise characteristics of the OP27 are achieved mainly by operating the input stage at a high quiescent current. The input
-12-
REV. C
OP27
1k OP08/108 500 5534 50 1 2 OP08/108 100
OP07
p-p NOISE - nV
1 100 OP27/37 50 2
1 RS e.g. RS 2 RS e.g. RS UNMATCHED = R S1 = 10k , R S2 = 0 MATCHED = 10k , R S1 = R S2 = 5k RS1
TOTAL NOISE - nV/ Hz
10
OP07 5534
5 OP27/37
1 RS e.g. RS 2 RS e.g. RS
UNMATCHED = R S1 = 10k , R S2 = 0 MATCHED = 10k , R S1 = R S2 = 5k RS1
REGISTER NOISE ONLY 10 50 100
RS2
REGISTER NOISE ONLY 50k 1 50 100
RS2
10k 500 1k 5k RS - SOURCE RESISTANCE -
10k 500 1k 5k RS - SOURCE RESISTANCE -
50k
Figure 5. Peak-to-Peak Noise (0.1 Hz to 10 Hz) as Source Resistance (Includes Resistor Noise)
Figure 6. 10 Hz Noise vs. Source Resistance (Includes Resistor Noise)
AUDIO APPLICATIONS
Therefore, for low-frequency applications, the OP07 is better than the OP27/OP37 when RS > 3 kW. The only exception is when gain error is important. Figure 6 illustrates the 10 Hz noise. As expected, the results are between the previous two figures. For reference, typical source resistances of some signal sources are listed in Table I.
Table I.
The following applications information has been abstracted from a PMI article in the 12/20/80 issue of Electronic Design magazine and updated. Figure 7 is an example of a phono pre-amplifier circuit using the OP27 for A1; R1-R2-C1-C2 form a very accurate RIAA network with standard component values. The popular method to accomplish RIAA phono equalization is to employ frequencydependent feedback around a high-quality gain block. Properly chosen, an RC network can provide the three necessary time constants of 3180, 318, and 75 ms.1 For initial equalization accuracy and stability, precision metal film resistors and film capacitors of polystyrene or polypropylene are recommended since they have low voltage coefficients, dissipation factors, and dielectric absorption.4 (High-K ceramic capacitors should be avoided here, though low-K ceramics-- such as NPO types, which have excellent dissipation factors and somewhat lower dielectric absorption--can be considered for small values.)
C4 (2) 220 F + + MOVING MAGNET CARTRIDGE INPUT Ra 47.5k Ca 150pF LF ROLLOFF OUT R5 100k
Device Strain Gauge Magnetic Tapehead
Source Impedance <500 W <1500 W
Comments Typically used in lowfrequency applications. Low is very important to reduce self-magnetization problems when direct coupling is used. OP27 IB can be neglected. Similar need for low IB in direct coupled applications. OP27 will not introduce any self-magnetization problem. Used in rugged servo-feedback applications. Bandwidth of interest is 400 Hz to 5 kHz.
Magnetic Phonograph Cartridges
<1500 W
Linear Variable <1500 W Differential Transformer
A1 OP27
C3 0.47 F
IN
R1 97.6k
R4 75k C1 0.03 F C2 0.01 F
OUTPUT
Open-Loop Gain
Frequency at 3 Hz 10 Hz 30 Hz
OP07 100 dB 100 dB 90 dB
OP27 124 dB 120 dB 110 dB
OP37 125 dB 125 dB 124 dB
R3 100
R2 7.87k
For further information regarding noise calculations, see "Minimization of Noise in Op Amp Applications," Application Note AN-15.
G = 1kHz GAIN R1 = 0.101 ( 1 + ) R3 = 98.677 (39.9dB) AS SHOWN
Figure 7. Phono Preamplifier Circuit
REV. C
-13-
OP27
The OP27 brings a 3.2 nV//Hz voltage noise and 0.45 pA//Hz current noise to this circuit. To minimize noise from other sources, R3 is set to a value of 100 W, which generates a voltage noise of 1.3 nV//Hz. The noise increases the 3.2 nV//Hz of the amplifier by only 0.7 dB. With a 1 kW source, the circuit noise measures 63 dB below a 1 mV reference level, unweighted, in a 20 kHz noise bandwidth. Gain (G) of the circuit at 1 kHz can be calculated by the expression: The network values of the configuration yield a 50 dB gain at 1 kHz, and the dc gain is greater than 70 dB. Thus, the worst-case output offset is just over 500 mV. A single 0.47 mF output capacitor can block this level without affecting the dynamic range. The tapehead can be coupled directly to the amplifier input, since the worst-case bias current of 80 nA with a 400 mH, 100 m inch head (such as the PRB2H7K) will not be troublesome. One potential tapehead problem is presented by amplifier biascurrent transients which can magnetize a head. The OP27 and OP37 are free of bias-current transients upon power-up or powerdown. However, it is always advantageous to control the speed of power supply rise and fall, to eliminate transients. In addition, the dc resistance of the head should be carefully controlled, and preferably below 1 kW. For this configuration, the bias-current-induced offset voltage can be greater than the 100pV maximum offset if the head resistance is not sufficiently controlled. A simple, but effective, fixed-gain transformerless microphone preamp ( Figure 9) amplifies differential signals from low impedance microphones by 50 dB, and has an input impedance of 2 kW. Because of the high working gain of the circuit, an OP37 helps to preserve bandwidth, which will be 110 kHz. As the OP37 is a decompensated device (minimum stable gain of 5), a dummy resistor, Rp, may be necessary, if the microphone is to be unplugged. Otherwise the 100% feedback from the open input may cause the amplifier to oscillate. Common-mode input-noise rejection will depend upon the match of the bridge-resistor ratios. Either close-tolerance (0.1%) types should be used, or R4 should be trimmed for best CMRR. All resistors should be metal film types for best stability and low noise. Noise performance of this circuit is limited more by the input resistors R1 and R2 than by the op amp, as R1 and R2 each generate a 4 nV//Hz noise, while the op amp generates a 3.2 nV//Hz noise. The rms sum of these predominant noise sources will be about 6 nV//Hz, equivalent to 0.9 mV in a 20 kHz noise bandwidth, or nearly 61 dB below a 1 mV input signal. Measurements confirm this predicted performance.
R1 1k R3 316k C1 5F R6 100
E R1 G = 0.101 A1 + E R3
For the values shown, the gain is just under 100 (or 40 dB). Lower gains can be accommodated by increasing R3, but gains higher than 40 dB will show more equalization errors because of the 8 MHz gain-bandwidth of the OP27. This circuit is capable of very low distortion over its entire range, generally below 0.01% at levels up to 7 V rms. At 3 V output levels, it will produce less than 0.03% total harmonic distortion at frequencies up to 20 kHz. Capacitor C3 and resistor R4 form a simple -6 dB-per-octave rumble filter, with a corner at 22 Hz. As an option, the switchselected shunt capacitor C4, a nonpolarized electrolytic, bypasses the low-frequency rolloff. Placing the rumble filter's high-pass action after the preamp has the desirable result of discriminating against the RlAA-amplified low-frequency noise components and pickup-produced low-frequency disturbances. A preamplifier for NAB tape playback is similar to an RIAA phono preamp, though more gain is typically demanded, along with equalization requiring a heavy low-frequency boost. The circuit in Figure 7 can be readily modified for tape use, as shown by Figure 8.
+
TAPE HEAD Ra Ca 0.47 F
OP27 -
R1 33k R2 5k 10 0.01 F
15k
T1 = 3180 s T2 = 50 s
Figure 8. Tape-Head Preamplifier
While the tape-equalization requirement has a flat high-frequency gain above 3 kHz (T2 = 50 ms), the amplifier need not be stabilized for unity gain. The decompensated OP37 provides a greater bandwidth and slew rate. For many applications, the idealized time constants shown may require trimming of R1 and R2 to optimize frequency response for nonideal tapehead performance and other factors.5
LOW IMPEDANCE MICROPHONE INPUT (Z = 50 TO 200 ) R3 = R4 R1 R2 R2 1k
Rp 30k
- OP27/ OP37 +
R4 316k
R7 10k
OUTPUT
Figure 9. Fixed Gain Transformerless Microphone Preamplifier
-14-
REV. C
OP27
For applications demanding appreciably lower noise, a high quality microphone transformer-coupled preamp (Figure 10) incorporates the internally compensated OP27. T1 is a JE-115K-E 150 W/15 kW transformer which provides an optimum source resistance for the OP27 device. The circuit has an overall gain of 40 dB, the product of the transformer's voltage setup and the op amp's voltage gain.
C2 1800pF R1 121 R2 1100
Capacitor C2 and resistor R2 form a 2 ms time constant in this circuit, as recommended for optimum transient response by the transformer manufacturer. With C2 in use, A1 must have unitygain stability. For situations where the 2 ms time constant is not necessary, C2 can be deleted, allowing the faster OP37 to be employed. Some comment on noise is appropriate to understand the capability of this circuit. A 150 W resistor and R1 and R2 gain resistors connected to a noiseless amplifier will generate 220 nV of noise in a 20 kHz bandwidth, or 73 dB below a 1 mV reference level. Any practical amplifier can only approach this noise level; it can never exceed it. With the OP27 and T1 specified, the additional noise degradation will be close to 3.6 dB (or -69.5 referenced to 1 mV).
References
T1* 150 SOURCE R3 100
A1 OP27
OUTPUT
* T1 - JENSEN JE - 115K - E JENSEN TRANSFORMERS 10735 BURBANK BLVD. N. HOLLYWOOD, CA 91601
1. Lipshitz, S.R, "On RIAA Equalization Networks," JAES, Vol. 27, June 1979, p. 458-481. 2. Jung, W.G., IC Op Amp Cookbook, 2nd. Ed., H.W. Sams and Company, 1980. 3. Jung, W.G., Audio IC Op Amp Applications, 2nd. Ed., H.W. Sams and Company, 1978. 4. Jung, W.G., and Marsh, R.M., "Picking Capacitors," Audio, February and March, 1980. 5. Otala, M., "Feedback-Generated Phase Nonlinearity in Audio Amplifiers," London AES Convention, March 1980, preprint 1976. 6. Stout, D.F., and Kautman, M., Handbook of Operational Amplifier Circuit Design, New York, McGraw-Hill, 1976.
Figure 10. High Quality Microphone TransformerCoupled Preamplifier
Gain may be trimmed to other levels, if desired, by adjusting R2 or R1. Because of the low offset voltage of the OP27, the output offset of this circuit will be very low, 1.7 mV or less, for a 40 dB gain. The typical output blocking capacitor can be eliminated in such cases, but is desirable for higher gains to eliminate switching transients.
+18V
OP27
-18V
Figure 11. Burn-In Circuit
REV. C
-15-
OP27
OUTLINE DIMENSIONS
8-Lead Plastic Dual-in-Line Package [PDIP] (N-8)
Dimensions shown in inches and (millimeters)
8-Lead Standard Small Outline Package [SOIC] Narrow Body (R-8)
Dimensions shown in millimeters and (inches)
0.375 (9.53) 0.365 (9.27) 0.355 (9.02)
8 5
5.00 (0.1968) 4.80 (0.1890)
0.295 (7.49) 0.285 (7.24) 0.275 (6.98) 0.325 (8.26) 0.310 (7.87) 0.300 (7.62) 0.015 (0.38) MIN SEATING PLANE 0.060 (1.52) 0.050 (1.27) 0.045 (1.14)
8 5 4
1
4
4.00 (0.1574) 3.80 (0.1497)
1
6.20 (0.2440) 5.80 (0.2284)
0.100 (2.54) BSC 0.180 (4.57) MAX 0.150 (3.81) 0.130 (3.30) 0.110 (2.79) 0.022 (0.56) 0.018 (0.46) 0.014 (0.36)
0.150 (3.81) 0.135 (3.43) 0.120 (3.05)
1.27 (0.0500) BSC 0.25 (0.0098) 0.10 (0.0040) COPLANARITY SEATING 0.10 PLANE
1.75 (0.0688) 1.35 (0.0532) 8 0.25 (0.0098) 0 0.19 (0.0075)
0.50 (0.0196) 0.25 (0.0099)
45
0.015 (0.38) 0.010 (0.25) 0.008 (0.20)
0.51 (0.0201) 0.33 (0.0130)
1.27 (0.0500) 0.41 (0.0160)
COMPLIANT TO JEDEC STANDARDS MS-012AA CONTROLLING DIMENSIONS ARE IN MILLIMETERS; INCH DIMENSIONS (IN PARENTHESES) ARE ROUNDED-OFF MILLIMETER EQUIVALENTS FOR REFERENCE ONLY AND ARE NOT APPROPRIATE FOR USE IN DESIGN
COMPLIANT TO JEDEC STANDARDS MO-095AA CONTROLLING DIMENSIONS ARE IN INCHES; MILLIMETERS DIMENSIONS (IN PARENTHESES)
8-Lead Ceramic DIP - Glass Hermetic Seal [CERDIP] (Q-8)
Dimensions shown in inches and (millimeters)
8-Lead Metal Can [TO-99] (H-08)
Dimensions shown in inches and (millimeters)
0.005 (0.13) MIN
8
0.055 (1.40) MAX
5
REFERENCE PLANE
0.1850 (4.70) 0.1650 (4.19)
0.5000 (12.70) MIN
0.2500 (6.35) MIN
PIN 1
1 4
0.310 (7.87) 0.220 (5.59)
0.3700 (9.40) 0.3350 (8.51)
0.1000 (2.54) BSC
0.0500 (1.27) MAX
0.1600 (4.06) 0.1400 (3.56) 0.0450 (1.14) 0.0270 (0.69)
5
0.3350 (8.51) 0.3050 (7.75)
0.100 (2.54) BSC 0.405 (10.29) MAX 0.200 (5.08) MAX 0.200 (5.08) 0.125 (3.18) 0.023 (0.58) 0.014 (0.36) 0.060 (1.52) 0.015 (0.38) 0.150 (3.81) MIN SEATING 0.070 (1.78) PLANE 0.030 (0.76) 15 0 0.015 (0.38) 0.008 (0.20) 0.320 (8.13) 0.290 (7.37)
4
6 7
0.2000 (5.08) BSC
3
2 8
0.0400 (1.02) MAX
0.0400 (1.02) 0.0100 (0.25)
0.0190 (0.48) 0.0160 (0.41)
0.1000 (2.54) BSC
1
0.0340 (0.86) 0.0280 (0.71)
0.0210 (0.53) 0.0160 (0.41)
45 BSC
BASE & SEATING PLANE
CONTROLLING DIMENSIONS ARE IN INCH; MILLIMETERS DIMENSIONS (IN PARENTHESES) ARE ROUNDED-OFF MILLIMETER EQUIVALENTS FOR REFERENCE ONLY AND ARE NOT APPROPRIATE FOR USE IN DESIGN
COMPLIANT TO JEDEC STANDARDS MO-002AK CONTROLLING DIMENSIONS ARE IN INCHES; MILLIMETERS DIMENSIONS (IN PARENTHESES) ARE ROUNDED-OFF EQUIVALENTS FOR REFERENCE ONLY AND ARE NOT APPROPRIATE FOR USE IN DESIGN
-16-
REV. C
OP27 Revision History
Location 1/03--Data Sheet changed from REV. B to REV. C. Page
Edits to PIN CONNECTIONS . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 1 Edits to GENERAL DESCRIPTION . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 1 Edits to DIE CHARACTERISTICS . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 5 Edits to ABSOLUTE MAXIMUM RATINGS . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 7 Updated OUTLINE DIMENSIONS . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 16
9/02--Data Sheet changed from REV. A to REV. B.
Edits to Figure 8 . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 14 Edits to OUTLINE DIMENSIONS . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 16
9/01--Data Sheet changed from REV. 0 to REV. A.
Edits to ORDERING INFORMATION . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 1 Edits to PIN CONNECTIONS . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 1 Edits to ABSOLUTE MAXIMUM RATINGS . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 2 Edits to PACKAGE TYPE . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 2 Edits to ELECTRICAL CHARACTERISTICS . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 2, 3 Edits to WAFER TEST LIMITS . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 4 Deleted TYPICAL ELECTRICAL CHARACTERISTICS . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 4 Edits to BURN-IN CIRCUIT figure . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 7 Edits to APPLICATION INFORMATION . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 8
REV. C
-17-
-18-
-19-
-20-
C00317-0-1/03(C)
PRINTED IN U.S.A.
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